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Compact substrate integrated waveguide (SIW) transversal filter with triple-mode microstrip resonator.pdf

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Compact Substrate Integrated Waveguide (SIW) Transversal Filter with Triple-Mode Microstrip Resonator Wei Shen 1, Wen-Yan Yin 2,1, Xiao-Wei Sun 3, and Jun-Fa Mao1 1 Center for Microwave and RF Technologies, School of Electronic Information and Electrical Engineering, Shanghai Jiao Tong University, Shanghai 200240, China weishen@sjtu.edu.cn 2 Center for Optical and Electromagnetic Research, State Key Lab of MOI, Zhejiang University 310058, China. wyyin@zju.edu.cn and wyyin@sjtu.edu.cn 3 Institute of Microsystem and Information Technology of Chinese Academy of Sciences, Shanghai 200050, China Abstract — A novel fourth-order substrate integrated waveguide (SIW) transversal filter with triple-mode microstrip resonator is presented. The triple-mode resonator is etched on the top metal layer of SIW cavity, so compact size can be achieved. The coupling scheme of filter exhibits transversal characteristic, and the design principle of the filter is simple. The filter has compact size and wide stopband in comparison with conventional SIW filters. An open stub was added on the port to get better frequency selectivity. Two SIW filter samples are designed and fabricated, with good agreement achieved between the measured and the simulated S-parameters. Index Terms—bandpass filter, coupling matrix, substrate integrated waveguide (SIW), S-parameters, transmission zeros, triple-mode. I. INTRODUCTION With the development of wireless and mobile communication systems, bandpass filters with better frequency selectivity and compact size have attracted much attention. Microstrip dual-mode filters were proposed for applications in communication systems [1] and [2]. Each dual-mode resonator acts as two resonators, therefore, the size may be reduced in comparison with conventional microstrip resonator. As the dual-mode filter proposed in [2], a transmission zero can move from the lower to higher stopband with the variation of length of open stub. A triple- mode filters with elliptic function and harmonic suppression was presented in [3]. Substrate integrated waveguide (SIW) filters have been studied extensively, which is duet to their low loss, low cost and easy integration with other passive components. Some planar SIW filters with elliptic function have been reported in [4]-[8]. Each of them takes planar SIW cavities as resonators, so the sizes of filters are large in comparison with microstrip filters. In this paper, we introduce a triple-mode resonator into SIW filter design to achieve compact size, which is etched on the top metal layer of SIW cavity. The proposed filter has two transmission zeros, but the transmission zero located at lower stopband is far away from passband. Therefore, an open stub is introduced on the port to get better frequency selectivity. The electric response is examined by theory of coupling matrix. Two filter samples with compact sizes, better frequency selectivity and wide stopband was fabricated and measured so as to validate the effectiveness of our proposed filters. II. DESIGN OF FILTER A. Triple-mode Resonator The layout of a triple-mode resonator is shown in Fig. 1 (a), and its equivalent layouts of odd- and even-modes are shown in Fig. 1 (b). The resonant frequencies of odd- and even- modes can be calculated by 1 1 1 2 odd cf Lε = (1a) 2 2 1 4 odd cf Lε = (1b) 1 2 1 ( 2 ) even cf L Lε = + (1c) Where evebf is resonant frequency of even-mode, and 1 oddf and 2oddf are resonant frequencies of two odd-modes, respectively. (a) (b) Fig. 1. Layout of (a) triple-mode resonator and (b) its equivalent odd- and even-modes, respectively. B. SIW Filter with Triple-mode Resonator Proceedings of Asia-Pacific Microwave Conference 2010 Copyright 2010 IEICE FR4B-3 1875 The top view and coupling scheme of the fourth-order with triple-mode resonator is shown in Figs. 2 (a) and (b), respectively. (a) (b) Fig.2. (a) Top view and (b) coupling scheme of the fourth-order filter with triple-mode resonator, respectively. As shown in Fig. 2 (b), the corresponding coupling matrix M can be written as [9] 1 2 3 4 1 11 1 2 22 2 3 33 3 4 44 4 1 2 3 4 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 = S S S S S L S L S L S L L L L L M M M M M M M M M M M M M M M M M M M M M The nodal admittance matrix is given by [9]: { [ ] [ ] [ ]}[ ] [ ][ ] [ ] + Ω + = = j G W M V A V j I (2) Here, [G] is a ( 2) ( 2)N N+ + matrix whose only nonzero entries are 11 2, 2 1N NG G + += = , [ ]M is the coupling matrix; [W] is a diagonal matrix of ( 2) ( 2)N N+ + , with 11 2, 2 0N NW W + += = , and 1kkW = . The S-parameters are determined by 1 11 1,11 2 [ ]S j A = + , 121 2,12 [ ]NS j A += (3a, 3b) The electric field achieves maximum at the open ends of triple-mode resonator. However, the electric field of SIW cavity is minimized at the area under the open ends. Therefore, the couplings between SIW and triple-mode resonator is weak. Its corresponding coupling matrix M is give by [9] 0 0.687 0.334 0.529 0.51 0 0.687 0 0 0 0 0.687 0.334 0 1.29 0 0 0.334 0.529 0 0 1.2 0 0.529 0.51 0 0 0 1.086 0.51 0 0.687 0.334 0.529 0.51 0 = M Fig.4. Synthesis frequency-dependent S-parameters for coupling matrixes. Figs. 3 shows the synthesized S-parameters for coupling matrix M . Then, two transmission zeros are obtained, which locate at 2.2 and 3.7 GHz, respectively. . DESIGN AND RESULTS The electric field distribution of filter is shown in Fig. 5. L1 and W1 are mainly used to control the bandwidth of the filter. The simulated S21-parameters of filter for different values of L1, W1, and L4 are plotted in Fig. 6 (a), (b), and (c), respectively. To achieve sharp skirt at the lower stopband, an open stub is used to obtain a transmission zero located at the lower stopband. L4 is used to control the location of the transmission zero. As Fig. 6 (a) shows, the bandwidth will increase with L1 increasing. Meanwhile, the transmission zero located at upper stopband will move close to passband. As shown in Fig. 6 (b), the bandwidth becomes narrow with W1 decreasing. This means the couplings between sources or load and triple-mode resonator will increase with L1 or W1 increasing. The parameter W2 is generally larger than W1 slightly. This ensures low radiation of SIW cavity. We can tune the couplings between source (load) and SIW or triple-mode resonator independently by tuning L2 and L3. In Fig. 6 (c), we can see that two transmission zeros can be obtained. The second one will move to passband with L4 shortening. Fig. 5 The configuration of the filter with triple-mode resonator. 1876 (a) (b) Fig. 6 The simulated S21-parameters for different values of (a) L1, (b) W1, and (b) L4, respectively. (a) (b) Fig. 7. The (a) photograph and (b) geometrical sizes of the fabricated filter, respectively. Two filter samples were fabricated on single-layered printed circuit board (PCB) with the thickness of 1mm, and its relative permittivity is 2.65ε = . Fig. 7 (a) and (b) show the photograph of the fabricated filter and its geometrical sizes, where the widths of the input and output 50 Ω microstrip lines are set to be 2.73 mm, respectively. The diameter of the via-holes is 1mm. The narrow band and wide band of S-parameters of the filter are plotted in Figs. 8 (a) and (b), respectively. The measured in-band return and insertion losses are below -18dB and about 1.6 dB, respectively. A transmission zeros is positioned at 3.75 GHz. And the second passband appears at 8.5 GHz, which is 2.57 times of the center frequency. It has wider stopband in comparison with conventional SIW filters. Because the harmonic passband is generally located at 1.6 times of center frequency, which is due to the TE102/TE201 mode. (a) 1877 (b) Fig. 8. The simulated and measured S-parameters of the proposed filter in (a) narrow band and (b) wide band, respectively. To improve the frequency selectivity of low stopband, an open stub is added at port. Then, an additional transmission zero will appear at lower stopband. The measured S- parameters are plotted in Fig. 9. The measured insertion and return losses are 1.9 and below 11 dB. Three transmission zeros located at 1.5, 2.5 and 3.75 GHz, respectively. The slight shift of center frequency is mainly contributed to the fabricated tolerance. The proposed filter with microstrip triple-mode resonator is very compact in comparison with conventional SIW filters. The filter has better frequency selectivity and wide stopband. Fig. 9 The simulated and measured S-parameters of the filter with an open- stub. Ⅳ. CONCLUSION In this paper, a compact SIW transversal filter with triple- mode resonator is presented, which is etched on the top metal layer of SIW cavity. An open stub is added on the port to improve the frequency selectivity. The transversal filter has better frequency selectivity and wide stopband in comparison with conventional SIW filters. Two filter samples were fabricated on single-layer PCB technology. Under such circumstances, better filter performance is achieved as demonstrated by our simulated as well as measured S- parameters. ACKNOWLEDGMENT This work was supported by the National Basic Research Program of China under Grant 2009CB320204. REFERENCES [1] L. Zhu and K. Wu, ‘‘A joint field/circuit model of line-to-ring coupling structures and its application to the design of microstrip dual-mode filters and ring resonator circuits,’’ IEEE Trans. Microw. Theory Tech., vol. 47, no. 10, pp. 1938---1948, Oct. 1999. [2] J. R. Lee, J. H. Cho, and S. W. Yun, ‘‘New compact bandpass filter using microstrip /4 resonators with open stub inverter,’’ IEEE Microw. Guide Wave Lett., vol. 10, no. 12, pp. 526-527, Dec. 2000. [3] W. Shen, X. W. Sun, and W. Y. Yin, “ A novel microstrip filter using three-mode stepped impedance resonator (TSIR),” IEEE Microw. Wirel. Compon. Lett., vol. 19, no. 12, pp. 774-776, Dec, 2009. [4] X. P. Chen and K.Wu, “Substrate integrated waveguide cross- coupled filter with negative coupling structure,” IEEE Trans. Microw. Theroy Tech., vol. 56, no. 1, pp. 142-149, 2008. [5] Z. C. Hao, W. Hong, X. P. Chen, J. X. Chen, K. Wu, and T. J. Cui, ‘‘Multilayered substrate integrated waveguide (MSIW) elliptic filter,’’ IEEE Microw. Wireless Compon. Lett., vol. 15, no. 2, pp. 95-97, Feb. 2005. [6] T. M. Shen, C. F. Chen, T. Y. Huang, and R. B. Wu, “Design of vertically stacked waveguide filters in LTCC,” IEEE Trans. Microw. Theroy Tech., vol. 55, no. 8, pp. 1771-1779, Aug. 2007. [7] B. J. Chen, T. M. Shen, and R. B. Wu, “Dual-band vertically stacked laminated waveguide filter design in LTCC technology,” IEEE Trans. Microw. Theroy Tech., vol. 57, no. 6, pp. 1554-1562, Jun. 2009. [8] W. Shen, L. S. Wu, X. W. Sun, W. Y. Yin, and J. F. Mao, “Novel substrate integrated waveguide filters with mixed cross coupling (MCC),” IEEE Microw. Wireless Compon. Lett., Vol. 19, No. 11, 701– 703, Nov. 2009. [9] S. Amari, U. Rosenberg, and J. Bornemann, “Adaptive synthesis and design of resonator filters with source/load-multi-resonator coupling,” IEEE Trans. Microw. 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