A FULLY PROTECTED PUSH-PULL CURRENT-FED
DC-DC CONVERTER
Alexander L. Rabello, Mircio A. C6, Gilbert0 C. D. Sousa and JosC L. F. Vieira
Universidade Federal do Espirito Santo
Departamento de Engenharia Eletrica - LEPAC - CP: 01-901 1
Vitdria - ES - Brazil - 29060-970
Phone: 55.27.335.2699 - Fax: 55.27.3 3 5.2650 - E-Mail: j oseluiz @ ele.ufes .br
Abstract - This paper presents an isolated dc-dc converter
designed to operate as a primary stage of an on-board dc-ac
power supply for diesel-electric engines. The dc-ac power supply
must provide a sinusoidal waveform of 127V rnls from 72V dc
bus of the engine. The dc-dc push-pull current-fed converter has
been used to obtain an isolated 200V dc output voltage from the
available 72V dc bus engine. This converter operates as a boost
converter with constant frequency and duty cycle greater than
50%. Two control loops operating in cascade mode were used. A
fast inner current loop regulates the boost inductor current.
Whereas an external control loop keeps a constant output
voltage. The experimental results have been obtained for a 300W
laboratory prototype operating at SOkHz. The converter
efficiency was 93% at full load, and the output voltage regulation
was less than 1 % for 10% to 100% load changes.
I. INTRODUCTION
Due to diesel-electric engine automation, different on-board
control equipments are required, which often need a regulated
ac power supply.
The diesel-electric engine provides 72V dc bus, which
varies between 58 to 85V. To function as an useful power
source this dc bus voltage must be converted to an ac voltage.
An ac power supply is essential to feed the measurement
instruments, which are employed to verify the behavior of all
on-board engine control equipments, under different operating
conditions, as well as the switching noise interferences
caused by the motor-generator set.
The block diagram of the complete dc-ac power supply is
presented in Fig.1. This paper discusses with the dc-dc
converter block only.
V i i i y f l DC-DC 1 dc 1-c
58-85 V ISoLA'IED 200V INWRTER 127V EILm BOOST dc
CONVERTER
-I I
Fig. 1 - Block diagram of the dc-ac power supply.
A dc-dc push-pull current-fed topology has been chosen,
since it provides isolation and low cost with high reliability.
Also, it can ensure high efficiency at low power
levels[l,2,3,4,5]. The dc-dc push-pull current-fed topology
operates as a boost converter with duty cycle greater than
50%. As can be seen in Fig. 2, the electrical isolation between
the engine's dc bus and the output voltage achieved through
by a high frequency transformer.
The control strategy is based on two cascade loops
dynamically separated, in which the current loop is faster than
the voltage loop [6]. This control strategy results in faster
responses to load changes, as well as to input voltage
variations compared to the conventional single voltage control
loop.
The use of a conventional single voltage control loop in a
boost converter results in a second-order transfer function
with a right half-plane zero. To prevent instabilities, a slowly
control-loop must be implemented.
As the two cascade loops present dynamic response faster
than the conventional one, low output-capacitance values can
be used, reducing the converter weight and size.
The converter reliability is improved by employing
protection circuits to prevent over-voltage, short-circuit and
over-current.
11. CIRCUIT DESCRIPTION
A. Power Stage:
The power stage diagram of the dc-dc push-pull current-fed
converter is shown in Fig.2. Its operation with duty cycle
greater than 50% is like the conventional boost converter. The
converter operation can be described by two stages, as
follows:
both switches are ON (b < t < tl and t2 < t < t3): the
voltage across the transformer primary is zero, and the
boost inductor current increases linearly, following the
equation:
(1)
one switch is ON (tl < t < t2 and t3 < t < t4): the voltage
across the transformer primary is q,, and the energy stored
by the boost inductor is delivered to the load. During this
stage the boost inductor current decreases linearly
according to the equation:
v, -V;
iL (t)= iL (ti)+ - (t - t l) (2)
b b r,
0-7803-3932-0
587
1
Yo
Fig.2 - Power stage diagram of the dc-dc push-pull
current-fed converter.
where:
SI, S2 - switches;
D1, Dz - output diodes;
Lb - boost inductance;
Vi" - input voltage;
vo - output voltage.
vb
NI, Nt
toll - switch conduction time;
tc - charging time;
td - discharging time;
T - switching period;
D
- output voltage reflected to the transformer primary
- transformei windings (n = NI&);
(V$VirJ;
- duty cycle ( D = t, / T).
The main waveforms of this converter are shown in Fig.3.
I I * t
e t '"p 1 w
t . i t t z t r L
Fig. 3 - Main waveforms: a, b) gate drive signals; c) boost
inductor current; d, e) switches currents; f) transformer
secondary current; g, h, i) voltage across: Lb, SI and Dz
respectively.
B. Control Stage:
The control scheme is based on two cascade loops
dynamically separated. A faster inner current loop regulates
the average current the boost inductor. For this control loop,
the output voltage reflected to the transformer primary can be
considered constant and equal to Vb.
The external loop maintains a constant output voltage,
independently of the load changes and the input voltage
variations. In this case, the output capacitance can be
considered fed by a constant current source.
By using this control strategy the two loops are reduced to
first order systems. These two cascade loops can be described
by two independent control loops, as shown in Fig. 4.
I
Fig. 4 - Control loop scheme: (a) - current loop;
(b) - voltage loop
C. Protection Stage:
Protection circuits, shown in Fig. 5, were implemented to
operate in case of anomalous conditions, such as:
over-voltage circuit: if the output voltage increases
beyond 15% of the rated value, the gate drive signals of
the MOSFETs are disabled by the over-voltage circuit.
over-current and short circuit: by using a voltage
comparator with hysteresis, the boost inductor current
can be maintained between a lower and an upper
bounds. If the output voltage drops bellow a specified
value, characterizing over-current or short-circuit, the
converter is shut-down after a given time period.
58 8
under-voltage lockout circuit: the MOSFElTs gate
circuits are kept out, at the converter start-up, until the
IC supply voltage has risen to 1OV.
- vcc $12v
vcc t
to MOSFET
gate circuit
I .......
14
Fig. 5 - Protections circuits: (a) over-voltage circuit,
(b) over-current and short-circuit, (c) under-voltage
lockout circuit (d) shutdown circuit
D. Complete Diagram of the dc-dc Converter:
The complete diagram of the dc-dc converter is shown in
Fig. 6. As can be seen, the control scheme is implemented
using just two ICs. The PWM regulator UC3527 IC provides
the gate drive signals to the MOSFETs. The control loop
regulators are accomplished by employing a Quad operational
amplifier TL074.
111. RELEVANT ANAJ..,ISYS
The average current through of the boost inductor can be
obtained from Fig. 3.c as:
- Z(t1) + Z(t2)
'Lb,avg - 2 (3)
The output current reflected to the transformer primary,
obtained from Fig. 3.f, is given by:
O T
The discharging time is given as follows:
(4)
From (3), (4) and (5) , it is obtained:
z; = 2 . z . ( l -D) U, "8
Considering Pi, = Pout, results in:
(7)
Substituting (6) in (7) the converter dc gain is obtained:
As can be seen from (8), in order to operate in the boost
mode (V: > Via), the following condition must be satisfied:
IV. EXPERIMENTAL, RESULTS
A laboratory prototype was built using the following data
specifications:
Input Voltage: V, = 58 to 85 Volts
Output Voltage: Vo = 200 +/- 5% V
Output power: Po = 300 W
Switching frequency: & = 50 kHz
58 9
71.8- I
Fig. 6
I 1
i startingcimrit VCC 4
- Complete diagram of the dc-dc
The experimental results were obtained for:
v,=5ov
vo=200v
Po=300W
f,=SOkHz
The steady state waveforms are shown in Fig. 7 and 8. The
switch S1 voltage and current are shown in Fig. 7. The switch
currents can be seen in Fig 8.
The transient waveforms are shown in Fig. 9 to Fig 13.
Fig. 9 shows the comp1t:te converter start up.
A detailed view of' the output voltage and the boost
inductor current at start up is shown in Fig. 10.
The output voltage and boost inductor current behavior
under load changes are shown in Fig. 11,
Fig. 12 shows the over current and short circuit protection
actuation. A complete start-up at short-circuit is shown in Fig.
13. Fig. 14 shows the converter efficiency as a function of the
output power.
converter.
Fig. 7 - S1 voltage and current; scales:
voltage: lOOV/div; current: SA/div
time: 2,Spddiv.
590
Fig. 8 - Switch currents; scales:
current: Wdiv., time: 2,5ps/div.
(a)
TeK Stop: sinele Sea 1oo)cys 17JW 1996
Tek Stou: Sinaie Sea 5.00kS/s 17Jun 1006
Fig. 9 - Complete output voltage and
boost inductor current start up;
scales: voltage: 1 OOV/div.;
current: 2A/div.; time: 50mddiv.
TeK Stou: sinde sea 1 o o ~ / s 17iun IQ96
Fig. 10 - Output voltage and boost inductor current
start up detail; scales: voltage: lOOV/div.,
current: 2A/div., time: 2.5ms/div.
(b)
Fig. 11 - The output voltage and the boost inductor
current for load steps:
(a) from 10% to 100% of the rated load;
(b) from 100% to 10% of the rated load; scales:
voltage: 2 V/div., current: 2A/div., time: 2,5ms/div.
TeK stop: smia sa I.OO~Q/S 24 JIM 10D6
Fig. 12 - The output voltage and boost inductor current for
the over current and the short protection circuits actuation;
scales: voltage: 5OV/div., current: SNdiv., time: 25Oms/div.
TBK Stop: Single Seq 2.5OkSls XJun 1006
b- 10:53:57
Fig. 13 - The output voltage and the boost inductor for a
complete start up at short circuit;
scalcs: voltage: lOV/div.
current: SA/div., time: 100ms/div.
Fig. 14 - Efficiency as a function of the output power.
V. CONCLUSIONS
This paper presented. a dc-dc isolated converter, which can
be employed as a primary stage for an on-board diesel-electric
engine dc-ac power supply.
Two control loops operating in cascade mode were used.
This control strategy results in faster responses to load
changes, as well as a better output voltage regulation. These
characteristics are achieved in spite of the fact that a low
value of output capacitance in use if compared to that of
conventional single voltage control loop.
The converter reliability is increased by incorporating over-
voltage, over-current and short-circuit protections.
The converter performance has been verified for a 300W
laboratory prototype operating at 5OkHz. The measured
efficiency was 93% and the output voltage regulation was less
than 1% for 10% to 1013% load changes. Consequently, it is an
attractive choice for on-board ac power supply.
ACKNOWLEDGMENT
The authors would like to express their gratitude to
“Thornton Inpec Eletrhica” Ltda. for contributing the
magnetic core for this project, and to “Autom6tica
Tecnologia” for the studentship support.
REFERENCE
[l] T.S.Latos and D.J.Bosac, “A High Efficiency 3kW
Switch Mode Battery Charger”, IEEE - PESC’82,
[2] R.Redl and N.O.Soka1, “Push-pull Current-Fed
Multiple-Output (regulated) DC-DC Power Converter with
only One Inductor and 0-100% Switching Duty Ratio”, IEEE-
[3] C.P.Henze, J.A.Smith and D.S. Lo, “A transformer
Isolated AC to DC Switch-Mode Power Converter with
Resistive Input Current”, IEEE Conference Publication,
[4] V.J. Thottuvelil, T.G. Wilson and H.A. Owen Jr,
“Analysis and Design of a Push-pull Current-Fed Converter”,
IEEE-PESC Record 1981, pp. 192-203.
[5] V.J. Thottuvelil, T.G. Wilson and H.A. Owen Jr,
“Small-Signal Modeling of a Push-Pull Fed-Current”, IEEE-
PESC Record 1982, pp. 225-239.
[6] Unitrode Integrate Circuits, “Products Applications
Handbook”, 1993-1994, Application Note, pp.9.457-9.468.
pp.341-349.
PESC’80, pp. 341-345.
N-.291, July 1988, pp. 428-439.
592
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