TDA2030A

TDA2030A 18W Hi-Fi AMPLIFIER AND 35W DRIVER October 2000 PENTAWATT ORDERING NUMBERS : TDA2030AH TDA2030AV  DESCRIPTION The TDA2030A is a monolithic IC in Pentawatt  package intended for use as low frequency class AB amplifier. With VS max = 44V it is particularly suited for more reliable applications without regulated supply and for 35W driver circuits using low-cost complemen- tary pairs. The TDA2030A provides high output current and has very low harmonic and cross-over distortion. Further the device incorporates a short circuit pro- tection system comprising an arrangement for automatically limiting the dissipatedpower so as to keep the working point of the output transistors within their safe operating area. A conventional thermal shut-down system is also included. TYPICAL APPLICATION 1/15 TEST CIRCUIT PIN CONNECTION (Top view) THERMAL DATA Symbol Parameter Value Unit Rth (j-case) Thermal Resistance Junction-case Max 3 °C/W TDA2030A 2/15 ABSOLUTE MAXIMUM RATINGS Symbol Parameter Value Unit Vs Supply Voltage ± 22 V Vi Input Voltage Vs Vi Differential Input Voltage ± 15 V Io Peak Output Current (internally limited) 3.5 A Ptot Total Power Dissipation at Tcase = 90 °C 20 W Tstg, Tj Storage and Junction Temperature – 40 to + 150 °C ELECTRICAL CHARACTERISTICS (Refer to the test circuit, VS = ± 16V,Tamb = 25oC unless otherwise specified) Symbol Parameter Test Conditions Min. Typ. Max. Unit Vs Supply Voltage ± 6 ± 22 V Id Quiescent Drain Current 50 80 mA Ib Input Bias Current VS = ± 22V 0.2 2 µA Vos Input Offset Voltage VS = ± 22V ± 2 ± 20 mV Ios Input Offset Current ± 20 ± 200 nA PO Output Power d = 0.5%, Gv = 26dB f = 40 to 15000Hz RL = 4Ω RL = 8Ω VS = ± 19V RL = 8Ω 15 10 13 18 12 16 W BW Power Bandwidth Po = 15W RL = 4Ω 100 kHz SR Slew Rate 8 V/µsec Gv Open Loop Voltage Gain f = 1kHz 80 dB Gv Closed Loop Voltage Gain f = 1kHz 25.5 26 26.5 dB d Total Harmonic Distortion Po = 0.1 to 14W RL = 4Ω f = 40 to 15 000Hz f = 1kHz Po = 0.1 to 9W, f = 40 to 15 000Hz RL = 8Ω 0.08 0.03 0.5 % % % d2 Second Order CCIF Intermodulation Distortion PO = 4W, f2 – f1 = 1kHz, RL = 4Ω 0.03 % d3 Third Order CCIF Intermodulation Distortion f1 = 14kHz, f2 = 15kHz 2f1 – f2 = 13kHz 0.08 % eN Input Noise Voltage B = Curve A B = 22Hz to 22kHz 2 3 10 µV µV iN Input Noise Current B = Curve A B = 22Hz to 22kHz 50 80 200 pA pA S/N Signal to Noise Ratio RL = 4Ω, Rg = 10kΩ, B = Curve A PO = 15W PO = 1W 106 94 dB dB Ri Input Resistance (pin 1) (open loop) f = 1kHz 0.5 5 MΩ SVR Supply Voltage Rejection RL = 4Ω, Rg = 22kΩ Gv = 26dB, f = 100 Hz 54 dB Tj Thermal Shut-down Junction Temperature 145 °C TDA2030A 3/15 Figure 3 : Output Power versus Supply Voltage Figure 4 : Total Harmonic Distortion versus Output Power (test using rise filters) Figure 1 : Single Supply Amplifier Figure 2 : Open Loop-frequency Response Figure 5 : Two Tone CCIF Intremodulation Distortion TDA2030A 4/15 Figure 6 : Large Signal Frequency Response Figure 7 : Maximum Allowable Power Dissipation versus Ambient Temperature Figure 10 : Output Power versus Input Level Figure 11 : Power Dissipation versus Output Power Figure 8 : Output Power versus Supply Voltage Figure 9 : Total Harmonic Distortion versus Output Power TDA2030A 5/15 Figure 12 : Single Supply High Power Amplifier (TDA2030A + BD907/BD908) Figure 13 : P.C.Board and Component Layout for the Circuit of Figure 12 (1:1 scale) TDA2030A 6/15 TYPICAL PERFORMANCE OF THE CIRCUIT OF FIGURE 12 Symbol Parameter Test Conditions Min. Typ. Max. Unit Vs Supply Voltage 36 44 V Id Quiescent Drain Current Vs = 36V 50 mA Po Output Power d = 0.5%, RL = 4Ω, f = 40 z to 15Hz Vs = 39V Vs = 36V d = 10%, RL = 4Ω, f = 1kHz Vs = 39V Vs = 36V 35 28 44 35 W W W W Gv Voltage Gain f = 1kHz 19.5 20 20.5 dB SR Slew Rate 8 V/µsec d Total Harmonic Distortion f = 1kHz Po = 20W f = 40Hz to 15kHz 0.02 0.05 % % Vi Input Sensitivity Gv = 20dB, f = 1kHz, Po = 20W, RL = 4Ω 890 mV S/N Signal to Noise Ratio RL = 4Ω, Rg = 10kΩ, B = Curve A Po = 25W Po = 4W 108 100 dB Figure 14 : Typical Amplifier with Spilt Power Supply Figure 15 : P.C.Board and Component Layout for the Circuit of Figure 14 (1:1 scale) TDA2030A 7/15 Figure 16 : Bridge Amplifier with Split Power Supply (PO = 34W, VS = ± 16V) Figure 17 : P.C.Board and Component Layout for the Circuit of Figure 16 (1:1 scale) MULTIWAY SPEAKER SYSTEMS AND ACTIVE BOXES Multiway loudspeaker systems provide the best possible acoustic performance since each loud- speaker is specially designed and optimized to handle a limited range of frequencies.Commonly, these loudspeaker systems divide the audio spec- trum into two or three bands. To maintaina flat frequencyresponseoverthe Hi-Fi audio range the bands covered by each loud- speaker must overlap slightly. Imbalance between the loudspeakers produces unacceptable results therefore it is important to ensure that each unit generates the correct amount of acoustic energy for its segmento of the audio spectrum. In this respect it is also important to know the energy distributionof the music spectrum to determine the cutoff frequenciesof the crossover filters (see Fig- ure 18). As an example a 100W three-way system with crossover frequencies of 400Hz and 3kHz would require 50W for the woofer, 35W for the midrange unit and 15W for the tweeter. TDA2030A 8/15 Figure 18 : Power Distribution versus Frequency Both active and passive filters can be used for crossovers but today active filters cost significantly less than a good passive filter using air cored inductors and non-electrolytic capacitors. In addi- tion, active filters do not suffer from the typical defectsof passive filters: - power less - increased impedance seen by the loudspeaker (lower damping) - difficulty of precise design due to variable loud- speaker impedance. Obviously, active crossovers can only be used if a power amplifier is provided for each drive unit. This makes it particularly interesting and economically sound to use monolithic power amplifiers. In some applications, complex filters are not really necessary and simple RC low-pass and high-pass networks (6dB/octave) can be recommended. The result obtained are excellent because this is the best type of audio filter and the only one free from phase and transient distortion. The rather poor out of band attenuation of single RC filtersmeansthat theloudspeakermustoperate linearly well beyond the crossover frequency to avoid distortion. Figure 19 : Active Power Filter A more effective solution, named ”Active Power Filter” by SGS-THOMSON is shown in Figure 19. The proposed circuit can realize combined power amplifiers and 12dB/octave or 18dB/octave high- pass or low-pass filters. In practice, at the input pins of the amplifier two equal and in-phase voltages are available, as re- quired for the active filter operation. The impedanceat the pin (-) is of the orderof 100Ω, while that of the pin (+) is very high, which is also what was wanted. The component values calculated for fc = 900Hz using a Bessek 3rd order Sallen and Key structure are : C1 = C2 = C3 R1 R2 R3 22nF 8.2kΩ 5.6kΩ 33kΩ Using this type ofcrossover filter, a complete3-way 60W active loudspeaker system is shown in Fig- ure 20. It employs 2nd order Buttherworth filters with the crossover frequencies equal to 300Hz and 3kHz. The midrange section consists of two filters, a high pass circuit followed by a low pass network. With VS = 36V the output power delivered to the woofer is 25W at d = 0.06% (30W at d = 0.5%). The power delivered to the midrange and the tweeter can be optimized in the design phase taking in account the loudspeaker efficiency and impedance (RL = 4Ω to 8Ω). It is quite common that midrange and tweeter speakers have an efficiency 3dB higher than- woofers. TDA2030A 9/15 Figure 20 : 3 Way 60W Active LoudspeakerSystem (VS = 36V) TDA2030A 10/15 MUSICAL INSTRUMENTS AMPLIFIERS Another important field of application for active systems is music. In this area the use of several medium power amplifiers is more convenient than a single high power amplifier, and it is also more realiable. A typical example (see Figure 21) consist of four amplifiers each driving a low-cost, 12 inch loud- speaker. This application can supply 80 to 160WRMS. Figure 21 : High Power Active Box for Musical Instrument TRANSIENT INTERMODULATION DISTOR- TION (TIM) Transient intermodulation distortion is an unfortu- natephenomenassociatedwithnegative-feedback amplifiers. When a feedbackamplifier receives an input signal which rises very steeply, i.e. contains high-frequencycomponents, the feedbackcan ar- rive too late so that the amplifiers overloads and a burst of intermodulationdistortion will be produced as in Figure 22. Since transients occur frequently in music this obviously a problem for the designer of audio amplifiers. Unfortunately, heavy negative feedback is frequency used to reduce the total harmonic distortion of an amplifier, which tends to aggravate the transient intermodulation (TIM situ- ation.The bestknownmethodfor the measurement of TIM consists of feeding sine waves superim- posed onto square waves, into the amplifier under test. The output spectrum is then examined using a spectrum analyser and compared to the input. This method suffers from serious disadvantages : theaccuracyis limited, the measurementis arather delicate operation and an expensive spectrum an- alyser is essential.A new approach (see Technical Note 143) applied by SGS-THOMSON to mono- lithic amplifiers measurement is fast cheap-it re- quires nothing more sophisticated than an oscilloscope - and sensitive - and it can be used down to the values as low as 0.002% in high power amplifiers. Figure 22 : Overshoot Phenomenonin Feedback Amplifiers The ”inverting-sawtooh” method of measurement is basedon theresponse of an amplifier to a 20kHz sawtooth waveform.The amplifier has no difficulty following the slow ramp but it cannot follow the fast edge. The output will follow the upper line in Fig- ure 23 cutting of theshaded area andthus increas- ing the mean level. If this output signal is filtered to remove the sawtooth,direct voltage remains which indicates the amount of TIM distortion, although it is difficult to measure because it is indistinguish- able from the DC offset of the amplifier. This prob- lem is neatly avoided in the IS-TIM method by periodically inverting the sawtooth waveform at a low audio frequency as shown in Figure 24. Figure 23 : 20kHzSawtooth Waveform Figure 24 : Inverting Sawtooth Waveform TDA2030A 11/15 In the case of the sawtooth in Figure 25 the mean level was increased by the TIM distortion, for a sawtooth in the other direction the opposite is true. The result is an AC signal at the output whole peak-to-peak value is the TIM voltage, which can be measured easily with an oscilloscope. If the peak-to-peak value of the signal and the peak-to- peak of the inverting sawtooth are measured, the TIM can be found very simply from: TIM = VOUTVsawtooth ⋅ 100 In Figure 25 the experimentalresults are shownfor the 30W amplifier using the TDA2030A as a driver and a low-cost complementary pair. A simple RC filter on the input of the amplifier to limit the maxi- mumsignal slope (SS) is an effectiveway to reduce TIM. Figure 25 : TIM Distortion versus Output Power The diagram of Figure 26 originated by SGS- THOMSONcan be used to find the Slew-Rate (SR) required for a given output power or voltage and a TIM design target. For example if an anti-TIM filter with a cutoff at 30kHz is used and the max. peak-to-peak output voltage is 20V then, referring to the diagram, a Slew-Rate of 6V/µs is necessary for 0.1% TIM. As shown Slew-Rates of above 10V/µs do not contribute to a further reduction in TIM. Slew-Rates of 100/µs are not only uselessbut also a disadvantage in Hi-Fi audio amplifiers because they tend to turn the amplifier into a radio receiver. Figure 26 : TIM Design Diagram (fC = 30kHz) POWER SUPPLY Using monolithic audio amplifier with non-regu- lated supply voltage it is important to design the power supply correctly. In any working case it must provide a supply voltage less than the maximum value fixed by the IC break-down voltage. It is essential to take into account all the working conditions,in particularmains fluctuationsand sup- ply voltage variations with and without load. The TDA2030A(VSmax = 44V) isparticularlysuitablefor substitution of the standard IC power amplifiers (withVS max = 36V) for more reliable applications. An example, using a simple full-wave rectifier fol- lowed by a capacitor filter, is shown in the table 1 and in the diagram of Figure 27. Figure 27 : DC Characteristics of 50W Non-regulated Supply TDA2030A 12/15 Table 2 Comp. Recom.Value Purpose Larger than Recommended Value Smaller than Recommended Value R1 22kΩ Closed loop gain setting Increase of gain Decrease of gain R2 680Ω Closed loop gain setting Decrease of gain (*) Increase of gain R3 22kΩ Non inverting input biasing Increase of input impedance Decrease of input impedance R4 1Ω Frequency Stability Danger of oscillation at high frequencies with inductive loads R5 ≅ 3 R2 Upper Frequency Cut-off Poor High Frequencies Attenuation Danger of Oscillation C1 1µF Input DC Decoupling Increase of low frequencies cut-off C2 22µF Inverting DC Decoupling Increase of low frequencies cut-off C3, C4 0.1µF Supply Voltage Bypass Danger of Oscillation C5, C6 100µF Supply Voltage Bypass Danger of Oscillation C7 0.22µF Frequency Stability Larger Bandwidth C8 ≈ 1 2piBR1 UpperFrequencyCut-off SmallerBandwidth LargerBandwidth D1, D2 1N4001 Toprotectthedeviceagainst output voltagespikes Table 1 Mains (220V) Secondary Voltage DC Output Voltage (Vo) Io = 0 Io = 0.1A Io = 1A + 20% 28.8V 43.2V 42V 37.5V + 15% 27.6V 41.4V 40.3V 35.8V + 10% 26.4V 39.6V 38.5V 34.2V – 24V 36.2V 35V 31V – 10% 21.6V 32.4V 31.5V 27.8V – 15% 20.4V 30.6V 29.8V 26V – 20% 19.2V 28.8V 28V 24.3V A regulatedsupply isnot usuallyused forthe power output stages becauseof its dimensioningmust be done taking into account the power to supply in the signal peaks.They are only a small percentage of the total music signal, with consequently large overdimensioning of the circuit. Even if with a regulated supply higher output power can be obtained(VS isconstant in all workingcondi- tions), the additional cost and power dissipation do not usually justify its use. Using non-regulated sup- plies,thereare fewerdesignerestriction.Infact,when signal peaks are present, the capacitor filter acts as a flywheel supplying the required energy. In average conditions, the continuous power sup- plied is lower. The music power/continuous power ratio is greater in this case than for the case of regulated supplied, with space saving and cost reduction. (*) The value of closed loop gain must be higher than 24dB. APPLICATION SUGGESTION The recommended values of the components are those shown on application circuit of Figure 14. Different values can be used.The Table 2 can help the designer. SHORT CIRCUIT PROTECTION The TDA2030A has an original circuit which limits the current of the output transistors. This function can be considered as being peak power limiting rather than simple current limiting. It reduces the possibility that the device gets damaged during an accidental short circuit from AC output to ground. THERMAL SHUT-DOWN The presence of a thermal limiting circuit offers the following advantages: 1. An overload on the output (even if it is permanent), or an above limit ambient temperaturecan be easily supportedsince the Tj cannot be higher than 150oC. 2. Theheatsinkcan havea smaller factorofsafety compared with that of a conventional circuit. There is no possibilityof devicedamagedue to high junction temperature.If forany reason, the junction temperature increases up to 150oC, the thermal shut-down simply reduces the power d iss ipa tion and the curren t consumption. TDA2030A 13/15 Weight: 2.00gr Pentawatt V DIM. mm inchMIN. TYP. MAX. MIN. TYP. MAX. A 4.8 0.189 C 1.37 0.054 D 2.4 2.8 0.094 0.110 D1 1.2 1.35 0.047 0.053 E 0.35 0.55 0.014 0.022 E1 0.76 1.19 0.030 0.047 F 0.8 1.05 0.031 0.041 F1 1.0 1.4 0.039 0.055 G 3.2 3.4 3.6 0.126 0.134 0.142 G1 6.6 6.8 7.0 0.260 0.268 0.276 H2 10.4 0.409 H3 10.05 10.4 0.396 0.409 L 17.55 17.85 18.15 0.691 0.703 0.715 L1 15.55 15.75 15.95 0.612 0.620 0.628 L2 21.2 21.4 21.6 0.831 0.843 0.850 L3 22.3 22.5 22.7 0.878 0.886 0.894 L4 1.29 0.051 L5 2.6 3.0 0.102 0.118 L6 15.1 15.8 0.594 0.622 L7 6.0 6.6 0.236 0.260 L9 2.1 2.7 0.008 0.106 L10 4.3 4.8 0.17 0.189 M 4.23 4.5 4.75 0.167 0.178 0.187 M1 3.75 4.0 4.25 0.148 0.157 0.167 V4 40° (typ.) V5 90° (typ.) Dia 3.65 3.85 0.144 0.152 L L1 A C L5 D1 L2 L3 E M1 MD H3 Dia. L7 L9 L10 L6 F1 H2 F G G1 E1 F E V4 RESIN BETWEEN LEADS H2 V5 V4 PENTVME L4 0015981 OUTLINE AND MECHANICAL DATA TDA2030A 14/15 Information furnished is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibility for the consequences of use of such information nor for any infringement of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specification mentioned in this publication are subject to change without notice. This publication supersedes and replaces all information previously supplied. STMicroelectronics products are not authorized for use as critical components in life support devices or systems without express written approval of STMicroelectronics. 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