DAC0830/DAC0832
8-Bit µP Compatible, Double-Buffered D to A Converters
General Description
The DAC0830 is an advanced CMOS/Si-Cr 8-bit multiplying
DAC designed to interface directly with the 8080, 8048,
8085, Z80®, and other popular microprocessors. A deposited
silicon-chromium R-2R resistor ladder network divides the
reference current and provides the circuit with excellent tem-
perature tracking characteristics (0.05% of Full Scale Range
maximum linearity error over temperature). The circuit uses
CMOS current switches and control logic to achieve low
power consumption and low output leakage current errors.
Special circuitry provides TTL logic input voltage level com-
patibility.
Double buffering allows these DACs to output a voltage cor-
responding to one digital word while holding the next digital
word. This permits the simultaneous updating of any number
of DACs.
The DAC0830 series are the 8-bit members of a family of
microprocessor-compatible DACs (MICRO-DAC™).
Features
n Double-buffered, single-buffered or flow-through digital
data inputs
n Easy interchange and pin-compatible with 12-bit
DAC1230 series
n Direct interface to all popular microprocessors
n Linearity specified with zero and full scale adjust
only — NOT BEST STRAIGHT LINE FIT.
n Works with ±10V reference-full 4-quadrant multiplication
n Can be used in the voltage switching mode
n Logic inputs which meet TTL voltage level specs (1.4V
logic threshold)
n Operates “STAND ALONE” (without µP) if desired
n Available in 20-pin small-outline or molded chip carrier
package
Key Specifications
n Current settling time: 1 µs
n Resolution: 8 bits
n Linearity: 8, 9, or 10 bits (guaranteed over temp.)
n Gain Tempco: 0.0002% FS/˚C
n Low power dissipation: 20 mW
n Single power supply: 5 to 15 VDC
Typical Application
BI-FET™ and MICRO-DAC™ are trademarks of National Semiconductor Corporation.
Z80® is a registered trademark of Zilog Corporation.
DS005608-1
May 1999
DAC0830/DAC0832
8-BitµP
Com
patible,Double-Buffered
D
to
A
Converters
© 1999 National Semiconductor Corporation DS005608 www.national.com
Connection Diagrams (Top Views)
Dual-In-Line and
Small-Outline Packages
DS005608-21
Molded Chip Carrier Package
DS005608-22
www.national.com 2
Absolute Maximum Ratings (Notes 1, 2)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
Supply Voltage (VCC) 17 VDC
Voltage at Any Digital Input VCC to GND
Voltage at VREF Input ±25V
Storage Temperature Range −65˚C to +150˚C
Package Dissipation
at TA=25˚C (Note 3) 500 mW
DC Voltage Applied to
IOUT1 or IOUT2 (Note 4) −100 mV to VCC
ESD Susceptability (Note 4) 800V
Lead Temperature (Soldering, 10 sec.)
Dual-In-Line Package (plastic) 260˚C
Dual-In-Line Package (ceramic) 300˚C
Surface Mount Package
Vapor Phase (60 sec.) 215˚C
Infrared (15 sec.) 220˚C
Operating Conditions
Temperature Range TMIN≤TA≤TMAX
Part numbers with “LCN” suffix 0˚C to +70˚C
Part numbers with “LCWM” suffix 0˚C to +70˚C
Part numbers with “LCV” suffix 0˚C to +70˚C
Part numbers with “LCJ” suffix −40˚C to +85˚C
Part numbers with “LJ” suffix −55˚C to +125˚C
Voltage at Any Digital Input VCC to GND
Electrical Characteristics
VREF=10.000 VDC unless otherwise noted. Boldface limits apply over temperature, TMIN≤TA≤TMAX. For all other limits
TA=25˚C.
Parameter Conditions SeeNote
VCC = 4.75 VDC
VCC = 15.75 VDC
VCC = 5 VDC ±5%
VCC = 12 VDC ±5%
to 15 VDC ±5% Limit
Units
Typ
(Note 12)
Tested
Limit
(Note 5)
Design
Limit
(Note 6)
CONVERTER CHARACTERISTICS
Resolution 8 8 8 bits
Linearity Error Max Zero and full scale adjusted 4, 8
−10V≤VREF≤+10V
DAC0830LJ & LCJ 0.05 0.05 % FSR
DAC0832LJ & LCJ 0.2 0.2 % FSR
DAC0830LCN, LCWM &
LCV
0.05 0.05 % FSR
DAC0831LCN 0.1 0.1 % FSR
DAC0832LCN, LCWM &
LCV
0.2 0.2 % FSR
Differential Nonlinearity Zero and full scale adjusted 4, 8
Max −10V≤VREF≤+10V
DAC0830LJ & LCJ 0.1 0.1 % FSR
DAC0832LJ & LCJ 0.4 0.4 % FSR
DAC0830LCN, LCWM &
LCV
0.1 0.1 % FSR
DAC0831LCN 0.2 0.2 % FSR
DAC0832LCN, LCWM &
LCV
0.4 0.4 % FSR
Monotonicity −10V≤VREF LJ & LCJ 4 8 8 bits
≤+10V LCN, LCWM & LCV 8 8 bits
Gain Error Max Using Internal Rfb 7 ±0.2 ±1 ±1 % FS
−10V≤VREF≤+10V
Gain Error Tempco Max Using internal Rfb 0.0002 0.0006 %
FS/˚C
Power Supply Rejection All digital inputs latched high
VCC=14.5V to 15.5V 0.0002 0.0025 %
11.5V to 12.5V 0.0006 FSR/V
4.5V to 5.5V 0.013 0.015
Reference Max 15 20 20 kΩ
Input Min 15 10 10 kΩ
Output Feedthrough Error VREF=20 Vp-p, f=100 kHz
All data inputs latched low 3 mVp-p
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Electrical Characteristics (Continued)
VREF=10.000 VDC unless otherwise noted. Boldface limits apply over temperature, TMIN≤TA≤TMAX. For all other limits
TA=25˚C.
Parameter Conditions SeeNote
VCC = 4.75 VDC
VCC = 15.75 VDC
VCC = 5 VDC ±5%
VCC = 12 VDC ±5%
to 15 VDC ±5% Limit
Units
Typ
(Note 12)
Tested
Limit
(Note 5)
Design
Limit
(Note 6)
CONVERTER CHARACTERISTICS
Output Leakage
Current Max
IOUT1 All data inputs LJ & LCJ 10 100 100 nA
latched low LCN, LCWM & LCV 50 100
IOUT2 All data inputs LJ & LCJ 100 100 nA
latched high LCN, LCWM & LCV 50 100
Output IOUT1 All data inputs 45 pF
Capacitance IOUT2 latched low 115
IOUT1 All data inputs 130 pF
IOUT2 latched high 30
DIGITAL AND DC CHARACTERISTICS
Digital Input Max Logic Low LJ: 4.75V 0.6
Voltages LJ: 15.75V 0.8
LCJ: 4.75V 0.7 VDC
LCJ: 15.75V 0.8
LCN, LCWM, LCV 0.95 0.8
Min Logic High LJ & LCJ 2.0 2.0 VDC
LCN, LCWM, LCV 1.9 2.0
Digital Input Max Digital inputs <0.8V
Currents LJ & LCJ −50 −200 −200 µA
LCN, LCWM, LCV −160 −200 µA
Digital inputs>2.0V
LJ & LCJ 0.1 +10 +10 µA
LCN, LCWM, LCV +8 +10
Supply Current Max LJ & LCJ 1.2 3.5 3.5 mA
Drain LCN, LCWM, LCV 1.7 2.0
Electrical Characteristics
VREF=10.000 VDC unless otherwise noted. Boldface limits apply over temperature, TMIN≤TA≤TMAX. For all other limits
TA=25˚C.
Symbol Parameter Conditions SeeNote
VCC=15.75 VDC
VCC=12 VDC±5%
to 15 VDC ±5%
VCC=4.75 VDC
VCC=5
VDC±5% Limit
UnitsTyp
(Note 12)
Tested
Limit
(Note 5)
Design Limit
(Note 6)
Typ
(Note 12)
Tested
Limit
(Note 5)
Design
Limit
(Note 6)
AC CHARACTERISTICS
ts Current Setting VIL=0V, VIH=5V 1.0 1.0 µs
Time
tW Write and XFER VIL=0V, VIH=5V 11 100 250 375 600
Pulse Width Min 9 320 320 900 900
tDS Data Setup Time VIL=0V, VIH=5V 9 100 250 375 600
Min 320 320 900 900
tDH Data Hold Time VIL=0V, VIH=5V 9 30 50 ns
Min 30 50
tCS Control Setup Time VIL=0V, VIH=5V 9 110 250 600 900
Min 320 320 1100 1100
tCH Control Hold Time VIL=0V, VIH=5V 9 0 0 10 0 0
Min 0 0
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. DC and AC electrical specifications do not apply when operating
the device beyond its specified operating conditions.
Note 2: All voltages are measured with respect to GND, unless otherwise specified.
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Electrical Characteristics (Continued)
Note 3: The maximum power dissipation must be derated at elevated temperatures and is dictated by TJMAX, θJA, and the ambient temperature, TA. The maximum
allowable power dissipation at any temperature is PD = (TJMAX − TA)/θJA or the number given in the Absolute Maximum Ratings, whichever is lower. For this device,
TJMAX = 125˚C (plastic) or 150˚C (ceramic), and the typical junction-to-ambient thermal resistance of the J package when board mounted is 80˚C/W. For the N pack-
age, this number increases to 100˚C/W and for the V package this number is 120˚C/W.
Note 4: For current switching applications, both IOUT1 and IOUT2 must go to ground or the “Virtual Ground” of an operational amplifier. The linearity error is degraded
by approximately VOS ÷ VREF. For example, if VREF = 10V then a 1 mV offset, VOS, on IOUT1 or IOUT2 will introduce an additional 0.01% linearity error.
Note 5: Tested limits are guaranteed to National’s AOQL (Average Outgoing Quality Level).
Note 6: Guaranteed, but not 100% production tested. These limits are not used to calculate outgoing quality levels.
Note 7: Guaranteed at VREF=±10 VDC and VREF=±1 VDC.
Note 8: The unit “FSR” stands for “Full Scale Range.” “Linearity Error” and “Power Supply Rejection” specs are based on this unit to eliminate dependence on a par-
ticular VREF value and to indicate the true performance of the part. The “Linearity Error” specification of the DAC0830 is “0.05% of FSR (MAX)”. This guarantees that
after performing a zero and full scale adjustment (see Sections 2.5 and 2.6), the plot of the 256 analog voltage outputs will each be within 0.05%xVREF of a straight
line which passes through zero and full scale.
Note 9: Boldface tested limits apply to the LJ and LCJ suffix parts only.
Note 10: A 100nA leakage current with Rfb=20k and VREF=10V corresponds to a zero error of (100x10−9x20x103)x100/10 which is 0.02% of FS.
Note 11: The entire write pulse must occur within the valid data interval for the specified tW, tDS, tDH, and tS to apply.
Note 12: Typicals are at 25˚C and represent most likely parametric norm.
Note 13: Human body model, 100 pF discharged through a 1.5 kΩ resistor.
Switching Waveform
DS005608-2
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Definition of Package Pinouts
Control Signals (All control signals level actuated)
CS: Chip Select (active low). The CS in combination
with ILE will enable WR1.
ILE: Input Latch Enable (active high). The ILE in combi-
nation with CS enables WR1.
WR1: Write 1. The active low WR1 is used to load the digi-
tal input data bits (DI) into the input latch. The data
in the input latch is latched when WR1 is high. To
update the input latch–CS and WR1 must be low
while ILE is high.
WR2: Write 2 (active low). This signal, in combination with
XFER, causes the 8-bit data which is available in
the input latch to transfer to the DAC register.
XFER: Transfer control signal (active low). The XFER will
enable WR2.
Other Pin Functions
DI0-DI7: Digital Inputs. DI0 is the least significant bit (LSB)
and DI7 is the most significant bit (MSB).
IOUT1: DAC Current Output 1. IOUT1 is a maximum for a
digital code of all 1’s in the DAC register, and is
zero for all 0’s in DAC register.
IOUT2: DAC Current Output 2. IOUT2 is a constant minus
IOUT1 , or IOUT1 + IOUT2 = constant (I full scale for
a fixed reference voltage).
Rfb: Feedback Resistor. The feedback resistor is pro-
vided on the IC chip for use as the shunt feedback
resistor for the external op amp which is used to
provide an output voltage for the DAC. This on-
chip resistor should always be used (not an exter-
nal resistor) since it matches the resistors which
are used in the on-chip R-2R ladder and tracks
these resistors over temperature.
VREF: Reference Voltage Input. This input connects an
external precision voltage source to the internal
R-2R ladder. VREF can be selected over the range
of +10 to −10V. This is also the analog voltage in-
put for a 4-quadrant multiplying DAC application.
VCC: Digital Supply Voltage. This is the power supply
pin for the part. VCC can be from +5 to +15VDC.
Operation is optimum for +15VDC
GND: The pin 10 voltage must be at the same ground
potential as IOUT1 and IOUT2 for current switching
applications. Any difference of potential (VOS pin
10) will result in a linearity change of
For example, if VREF = 10V and pin 10 is 9mV offset from
IOUT1 and IOUT2 the linearity change will be 0.03%.
Pin 3 can be offset ±100mV with no linearity change, but the
logic input threshold will shift.
Linearity Error
Definition of Terms
Resolution: Resolution is directly related to the number of
switches or bits within the DAC. For example, the DAC0830
has 28 or 256 steps and therefore has 8-bit resolution.
Linearity Error: Linearity Error is the maximum deviation
from a straight line passing through the endpoints of the
DAC transfer characteristic. It is measured after adjusting for
zero and full-scale. Linearity error is a parameter intrinsic to
the device and cannot be externally adjusted.
National’s linearity “end point test” (a) and the “best straight
line” test (b,c) used by other suppliers are illustrated above.
The “end point test’’ greatly simplifies the adjustment proce-
dure by eliminating the need for multiple iterations of check-
ing the linearity and then adjusting full scale until the linearity
is met. The “end point test’’ guarantees that linearity is met
after a single full scale adjust. (One adjustment vs. multiple
iterations of the adjustment.) The “end point test’’ uses a
standard zero and F.S. adjustment procedure and is a much
more stringent test for DAC linearity.
Power Supply Sensitivity: Power supply sensitivity is a
measure of the effect of power supply changes on the DAC
full-scale output.
Settling Time: Settling time is the time required from a code
transition until the DAC output reaches within ±1⁄2LSB of the
final output value. Full-scale settling time requires a zero to
full-scale or full-scale to zero output change.
Full Scale Error: Full scale error is a measure of the output
error between an ideal DAC and the actual device output.
Ideally, for the DAC0830 series, full scale is VREF −1LSB.
For VREF = 10V and unipolar operation, VFULL-SCALE =
10,0000V–39mV 9.961V. Full-scale error is adjustable to
zero.
DS005608-23
a) End point test after
zero and fs adj.
DS005608-24
b) Best straight line DS005608-25
c) Shifting fs adj. to pass
best straight line test
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Definition of Terms (Continued)
Differential Nonlinearity: The difference between any two
consecutive codes in the transfer curve from the theoretical
1 LSB to differential nonlinearity.
Monotonic: If the output of a DAC increases for increasing
digital input code, then the DAC is monotonic. An 8-bit DAC
which is monotonic to 8 bits simply means that increasing
digital input codes will produce an increasing analog output.
Typical Performance Characteristics
DS005608-4
FIGURE 1. DAC0830 Functional Diagram
Digital Input Threshold
vs. Temperature
DS005608-26
Digital Input Threshold
vs. VCC
DS005608-27
Gain and Linearity Error
Variation vs. Temperature
DS005608-28
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Typical Performance Characteristics (Continued)
DAC0830 Series Application Hints
These DAC’s are the industry’s first microprocessor compat-
ible, double-buffered 8-bit multiplying D to A converters.
Double-buffering allows the utmost application flexibility from
a digital control point of view. This 20-pin device is also pin
for pin compatible (with one exception) with the DAC1230, a
12-bit MICRO-DAC. In the event that a system’s analog out-
put resolution and accuracy must be upgraded, substituting
the DAC1230 can be easily accomplished. By tying address
bit A0 to the ILE pin, a two-byte µP write instruction (double
precision) which automatically increments the address for
the second byte write (starting with A0=“1”) can be used.
This allows either an 8-bit or the 12-bit part to be used with
no hardware or software changes. For the simplest 8-bit ap-
plication, this pin should be tied to VCC (also see other uses
in section 1.1).
Analog signal control versatility is provided by a precision
R-2R ladder network which allows full 4-quadrant multiplica-
tion of a wide range bipolar reference voltage by an applied
digital word.
1.0 DIGITAL CONSIDERATIONS
A most unique characteristic of these DAC’s is that the 8-bit
digital input byte is double-buffered. This means that the
data must transfer through two independently controlled 8-bit
latching registers before being applied to the R-2R ladder
network to change the analog output. The addition of a sec-
ond register allows two useful control features. First, any
DAC in a system can simultaneously hold the current DAC
data in one register (DAC register) and the next data word in
the second register (input register) to allow fast updating of
the DAC output on demand. Second, and probably more im-
portant, double-buffering allows any number of DAC’s in a
system to be updated to their new analog output levels si-
multaneously via a common strobe signal.
The timing requirements and logic level convention of the
register control signals have been designed to minimize or
eliminate external interfacing logic when applied to most
popular microprocessors and development systems. It is
easy to think of these converters as 8-bit “write-only”
memory locations that provide an analog output quantity. All
inputs to these DAC’s meet TTL voltage level specs and can
also be driven directly with high voltage CMOS logic in
non-microprocessor based systems. To prevent damage to
the chip from static discharge, all unused digital inputs
should be tied to VCC or ground. If any of the digital inputs
are inadvertantly left floating, the DAC interprets the pin as a
logic “1”.
1.1 Double-Buffered Operation
Updating the analog output of these DAC’s in a
double-buffered manner is basically a two step or double
write operation. In a microprocessor system two unique sys-
tem addresses must be decoded, one for the input latch con-
trolled by the CS pin and a second for the DAC latch which
is controlled by the XFER line. If more than one DAC is being
driven, Figure 2, the CS line of each DAC would typically be
decoded individually, but all of the converters could share a
common XFER address to allow simultaneous updating of
any number of DAC’s. The timing for this operation is shown,
Figure 3.
It is important to note that the analog outputs that will change
after a simultaneous transfer are those from the DAC’s
whose input register had been modified prior to the XFER
command.
Gain and Linearity Error
Variation vs. Supply Voltage
DS005608-29
Write Pulse Width
DS005608-30
Data Hold Time
DS005608-31
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DAC0830 Series Application Hints (Continued)
The ILE pin is an active high chip select which can be de-
coded from the address bus as a qualifier for the normal CS
signal generated during a write operation. This can be used
to provide a higher degree of decoding unique control sig-
nals for a particular DAC, and thereby create a more efficient
addressing scheme.
Another useful application of the ILE pin of each DAC in a
multiple DAC system is to tie these inputs together and use
this as a control line that can effectively “freeze” the outputs
of all the DAC’s at their present value. Pulling this line low
latches the input register and prevents new data from being
written to the DAC. This can be particularly useful in multi-
processing systems to allow a processor other than the one
controlling the DAC’s to take over control of the data bus and
control lines. If this second system were to use the same ad-
dresses as those decoded for DAC control (but for a different
purpose) the ILE function would prevent the DAC’s from be-
ing erroneously altered.
In a “Stand-Alone” system the control signals are generated
by discrete logic. In this case double-buffering can be con-
trolled by simply taking CS and XFER to a logic “0”, ILE to a
logic “1” and pulling WR1 low to load data to the input latch.
Pulling WR2 low will then update the analog output. A logic
“1” on either of these lines will prevent the changing of the
analog output.
DS005608-35
*TIE TO LOGIC 1 IF NOT NEEDED (SEE SEC. 1.1).
FIGURE 2. Controlling Mutiple DACs
DS005608-36
FIGURE 3.
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DAC0830 Series Application Hints (Continued)
1.2 Single-Buffered Operation
In a microprocessor controlled system where maximum data
throughput to the DAC is of primary concern, or when only
one DAC of several needs to be updated at a time, a
single-buffered configuration can be used. One of the two in-
ternal registers allows the data to flow through and the other
register will serve as the data latch.
Digital signal feedthrough (see Section 1.5) is minimized if
the input register is used as the data latch. Timing for this
mode is shown in Figure 4.
Single-buffering in a “stand-alone” system is achieved by
strobing WR1 low to update the DAC with CS, WR2 and
XFER grounded and ILE tied high.
1.3
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